onsemi NCP1230 90 Watt Universal Input Adapter Power Supply Evaluation Board User Manual

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EVAL BOARD USER’S MANUAL

NCP1230 90 Watt Universal Input Adapter Power Supply Evaluation Board

NCP1230GEVB
NCP1230 90 Watt, Universal
Input Adapter Power Supply
Evaluation Board User’s Manual

General Description

The NCP1230 implements a standard current mode control architecture. It’s an ideal candidate for applications where a low parts count is a key parameter, particularly in low cost adapter power supplies. The NCP1230 combines a low standby power mode with an event management scheme that will disable a PFC circuit during Standby, thus reducing the no load power consumption. The 90 W Evaluation Board demonstrates the wide range of features found on the NCP1230 controller.
The NCP1230 has a PFC_Vcc output pin which provides Vcc power for a PFC controller, or other circuitry. The PFC_Vcc pin is enabled when the output of the power supply is up and in regulation. In the event that there is an output fault, the PFC_Vcc pin is turned off, disabling the PFC controller, reducing the stress on the PFC semiconductors.
In addition to excellent no load power consumption, the NCP1230 provides an internal latching function that can be used for over voltage protection by pulling the CS pin above 3.0 V.
Features

• Current−Mode Control
• Lossless Startup Circuit
• Operation Over the Universal Input Range
• Direct Connection to PFC Controller
• Low Standby
• Overvoltage Protection

![onsemi NCP1230 90 Watt Universal Input Adapter Power Supply Evaluation Board

• figure 1](https://manuals.plus/wp-content/uploads/2024/01/onsemi-NCP1230-90 -Watt-Universal-Input-Adapter-Power-Supply-Evaluation-Board-figure-1.png)

Design Specification

This Demo Board is configured as a two stage adapter power supply. The first stage operates off of the universal input, 85−265 Vac, 50−60 Hz, using the MC33260 Critical Conduction Mode controller, in the Boost Follower mode. The output voltage from the Boost Follower (when Vin is 85 Vac) is 200 V and as the input line increases to 230 Vac the output of the Boost Follower will ramp up to 400 Vdc.
The second stage of the power supply features the NCP1230 driving a flyback power stage. The output of the second stage is 19 Vdc capable of 90 W of output power. It is fully self−contained and includes a bias supply that operates off of the Auxiliary winding of the transformer.
Table 1. EVALUATION BOARD SPECIFICATIONS

Pin Short Circuit Load
Vin 230 Vac| mW| | 100
Pin with 0.5 W Load
Vin 230 Vac| mW| | 0.8

PFC
The MC33260 is configured as a Boost Follower operating from the universal input line. The PFC section was designed to provide approximately 116 W of power. NCP1230GEVB
The MC33260 is a Critical Conduction Mode controller; as a result the switching frequency is a function of the boost inductor and the timing capacitor. In this application the minimum operating frequency is 30 kHz.The value used is 400 μH.
Where:The oscillator timing capacitor is calculated by the following formula:Where:
Kosc = 6400
Ro = 2.0 MΩ (feedback resistor)
The CT value used is 820 pF
Refer to the ON Semiconductor website for Application Note AND8123/D for additional MC33260 application information, and the Excel based development tool DDTMC33260/D.
Startup Circuit Description
The High Voltage pin (pin 8) of the NCP1230 controller is connected directly to the high voltage DC bus. When the input power is turned on, an internal current source is turned on (typically 3.0 mA) charging up an external capacitor on the Vcc pin. When the Vcc capacitor is above VCCoff, the current source is turned off, and the controller delivers output drive pulses to an external MOSFET, Q1. The MOSFET, Q1, drives the primary of the transformer T1. The transformer has two additional windings, the auxiliary
winding which provides power to the controller after the power supply is running, and the secondary winding which provided the 19 Vdc output power.
Transformer
The transformer primary inductance was selected so the current would be discontinuous under all operating conditions. As a result the total switching period, Ton + Toff, must be less than or equal to 1/frequency.
The following assumptions were used in the design process: Dmax = 0.4 Duty Cycle
Vdc bus = 200 Vdc input with Vin 85 Vac
Efficiency = 0.80
Freq = 65 kHz
Vo = 19 V
Vf = 0.7
Po = 90 W In this application the primary inductance used is 220 μH. This takes into consideration the transformer tolerances, and to minimize the transformer size. Once the primary inductance has been calculated, the next step is to determine the peak primary current. The following calculations are used to verify that the current will be Discontinuous under all operating conditions.With a primary inductance value of 220 μH, Ton + Toff is less than the controller switching period. An Excel spreadsheet was designed using the above equation to help calculate the correct primary inductance value; visit the ON Semiconductor website for a copy of the spreadsheet.
One method for calculating the transformer turns ratio is to minimize the voltage stress of the MOSFET (VDS) due to the reflected output voltage.
V DSmax =Vinmax + n·(Vo+ Vf) +Vspike
In this application an 800 V MOSFET was selected. The goal, for safety purposes, is to limit VDSmax at high line (including the Vspike) to 700 V. To limit the power dissipation in the snubber clamp (refer to the section in the Applications Note titled “Snubber”.) Vspike is clamped at 167 V.
![onsemi NCP1230 90 Watt Universal Input Adapter Power Supply Evaluation Board

• fig 8](https://manuals.plus/wp-content/uploads/2024/01/onsemi-NCP1230-90 -Watt-Universal-Input-Adapter-Power-Supply-Evaluation-Board-fig-8.png)The NCP1230 requires that the controller Vcc be supplied through an auxiliary winding on the transformer. The nominal supply voltage for the controller is 13 Vdc. The supply voltage to the controller may be higher than the calculated value because of the transformer leakage inductance. The leakage inductance spike on the auxiliary winding is averaged by the rectifier D2 and capacitor C5. Because of this, an 18 V Zener diode (D18 refer to the Demo Board Schematic Figure 10) is connected from the Vcc pin to ground. To limit the current into the Zener diode a 200Ω resistor is placed between C5 and the Vcc pin (R28). ON Semiconductor recommends that the Vcc capacitor be at least 47 μF to be sure that the Vcc supply voltage does not drop below Vccmin (7.6 V typical) during standby power mode and unusual fault conditions.
  The transformer primary rms current is:The transformer secondary rms current is:The transformer for the Demo Board was manufactured by Cooper Electronics Technologies (www.cooperET.com) part number CTX22−16134. The designer should take precautions that under startup conditions, the transformer will not saturate at the low input ac line (85 Vac) and full load conditions. The above calculation assumed that the adapter was running and the PFC front end was enabled.
  Output Filter
  One of the disadvantages of a Flyback converter operating in the Discontinuous mode is there is a large ripple current in the output capacitor(s). As a result you may be required to use multiple capacitors in parallel to handle the ripple current.In the 90 W Adapter design four 2200 μF (8800 μF total) capacitors (C2, C3, C14, and C15) were required in parallel to handle the ripple current.
  A small LC filter has been added to the output of the power supply to help reduce the output ripple. The cut−off frequency for the filter is:

Output Rectifying Diode
The rectifying diode was selected based upon on the peak inverse voltage and the diodes average forward current. The peak inverse voltage across the secondary of the transformer is: The average current through the diode is: An MBR20100CT Schottky diode was selected; it is rated for a VRRM of 100 V, with an average forward current of 10 A.
Power Switch
A MOSFET was selected as the power switching element.
Several factors were used in selecting the MOSFET; current, voltage stress (VDS), and RDS(on) .
The rms current through the primary of the transformer is the same as the current in the MOSFET, which is 1.45 Arms.
The MOSFET selected is manufactured by Infineon, part number SPP11N80C3. It is rated for 800 VDS and 11 Arms, with an R DS(on) of 0.45Ω.

Snubber
The maximum voltage across the MOSFET is:This calculation neglects the voltage spike when the MOSFET turns off due to the transformer leakage inductance. The spike, due to the leakage inductance, must be clamped to a level below the MOSFETs’ maximum VDS. To clamp the voltage spike a resistive, capacitive, diode clamp network was used to prevent the drain voltage from rising above Vin + (Vo + Vf) n + Vclamp. The desired clamp voltage is 700 V; this provides a safety margin of 100 V. The first step is to calculate the snubber resistor.
![onsemi NCP1230 90 Watt Universal Input Adapter Power Supply Evaluation Board

• fig 17](https://manuals.plus/wp-content/uploads/2024/01/onsemi-NCP1230-90 -Watt-Universal-Input-Adapter-Power-Supply-Evaluation-Board-fig-17.png)Where:
  Vo = the output voltage
  Vf = the forward voltage drop across the output diode
  n is the transformer turns ratio 6.77
  Ie is the transformer turns ratio of 7 μH
  The power dissipation in the clamp resistor is:The snubber capacitor can be calculated from the following equation. See Application Note AN1679/D for details of how the snubber equations were derived. After the initial snubber was calculated, the snubber values were tuned in the circuit to minimize ringing, and minimize the power dissipation. As a result the final circuit values are; Rclamp uses three 100 kΩ (33 kΩ equivalent), 2.0 W resistors used in parallel, and C6 is 0.01 μF, 1000 V. Refer to Figure 2 for a scope waveform of the Drain to source voltage at full load and high line. Current Sense Resistor Selection
  The input to the current sense amplifier is clamped to 1.0 V (typical). The current sense resistor should be calculated at 125% of the full rated load to be sure that under all operating conditions the power supply will be able to deliver the full rated power. 0.2 Ω was used.
  To reduce the power dissipation in the sense resistor, two
  0.4Ω resistors were used in parallel.
  Overvoltage Protection
  The NCP1230 has a fast comparator which only monitors the current sense pin during the power switch off time. If the voltage on the current sense pin rises above 3.0 V (typical), the NCP1230 will immediately stop the output drive pulses and latch−off the controller. The NCP1230 will stay in the Latch−Off mode until Vcc has dropped below 4.0 V.
  This feature allows the user to implement several protection functions, for example, Overvoltage or Overtemperature Protection.
  The Auxiliary winding of the Flyback transformer (T5) can be used for overvoltage protection because the voltage on the Auxiliary winding is proportional to the output voltage.
  To implement Overvoltage Protection (OVP), a PNP transistor is used to bias up the current sense pin during the NCP1230 controller off time (refer to Figure 3). The base of the PNP transistor is driven by the NCP1230 drive output (pin 5), if the Auxiliary winding voltage increases above the Zener diode (D1) breakdown voltage, 13 V, current will flow through Q3 biasing up the voltage on the current sense pin. Using typical component values, if the voltage on the Auxiliary winding reaches 16.5 V (3.5 V above the nominal voltage) the NCP1230 will latch−off through the CS input (pin 3).A 13 V Zener diode was selected to have the controller Latch−Off prior to having Vcc reach its maximum allowable voltage level, 18 V.

Figure 3. Overvoltage Protection Circuit

Overtemperature Protection

To implement Overtemperature Protection (OTP) shutdown, the Zener diode can be replaced by an NTC (refer to Figure 4), or an NTC can be placed in parallel with the Zener diode to have OVP and OTP protection. When an overtemperature condition occurs, the resistance of the NTC will decrease, allowing current to flow through the PNP transistor biasing up the Current Sense pin.Figure 4. Overtemperature Protection Circuit

Slope Compensation

A Flyback converter operating in continuous conduction mode with a duty cycle greater than 50% requires slope compensation. In this application the power supply will always be operating in the discontinuous mode, so no slope compensation is required.
The resistor R21 and capacitor C24 form a low pass filter suppressing the leading edge of the current signal. Typically, the leading edge of the current will have a large spike due to the transformer leakage inductance. If the spike is not filtered, it can prematurely turn off the MOSFET. The NCP1230 does have a leading edge blanking circuit, but it is a good design practice to add an external filter. The time constant of the filter must be significantly higher than the highest expected operating frequency, but low enough to filter the spike.

Output Control

Feedback theory states that for the control loop to be stable there must be at least 45° of phase margin when the loop gain crosses cross zero dB. The following equations derive the Flyback converter transfer function while operating in the discontinuous continuous mode. Where:
Po is the maximum output power
Vo is the output voltage
Ro is the output resistance Where:
I is the peak primary current
Lp is the transformer primary inductance
F is the switching frequency of the controller Where:
Ip is the peak primary current
Rs is the current sense resistor
Vc is the control voltage
3, the feedback input voltage is divided down by a factor of three
Combining equations the open loop gain is:With current mode control, there is pole associated with the output capacitor(s) and the load resistors. In this application there are four 2200 μF capacitors in parallel:The secondary filter made up of L1 and C8 does not affect the control loop because we are sensing the output voltage before the LC network.
In addition to the pole, there is a zero associated with the output capacitor(s) and the capacitors esr. The esr of each capacitors is 0.022 Ω (from the data sheet).A small 0.47 nF capacitor (C25) is connected from the feedback pin to ground to reduce the switching noise on the feedback pin. Care must be taken not to have too large a capacitor, or a low frequency pole may be created in the feedback loop.

Output Voltage Regulation

The output voltage regulation is achieved by using a TL431 on the secondary side of the transformer. The output voltage is sensed and divided down to the reference level of the TL431 (2.5 V typical) by the resistive divider network consisting of R4 and R10.
The TL431 requires a minimum of 1.0 mA of current for regulation:In this application R22 was changed to 1.0 kΩ to minimize the stand by power consumption.
When the power supply is operating at no load, there may not be sufficient current through the optocoupler LED, so a  esistor (R7) is placed in parallel. A 4.7 kΩ resistor was selected.
The optocoupler gain is:CTR is the current transfer ratio of the opto and is nominally 1.0, but over time the CTR will degrade so analysis of the circuit with the CTR = 0.5 is recommended. Rfb is the internal pull−up resistor of the NCP1230 and it is a nominal 20 kΩ.

Standby Power
To minimize the standby power consumption, the output voltage sense resistor divider network was select to consume less than 10 mW.The Standby power consumption is:Standby power calculation:

Control Loop

Two methods were used to verify that the Demo Board loop was stable, the results are shown below. The first method was to use an Excel Spreadsheet (using the previously derived equations) which can be down loaded from the ON Semiconductor website (www.onsemi.com).
The results from the Excel Spreadsheet are shown below. At full load and 200 Vdc (200 Vdc is the minimum voltage being supplied from the PFC) the loop gain crosses zero dB at approximately 1.2 kHz with approximately 100° of phase margin.
The second method was to model the NCP1230 Demo Board in PSPICE. The result can be seen in Figure 7.
Because parasitic elements can be added to the PSPICE model, it was more accurate at high frequencies. The results from the PSPICE model (at low frequencies) shows similar results, the loop gain crosses zero dB at approximately 1.2 kHz with about 90° of phase margin.Figure 5. Excel Spreadsheet Loop Gain

Evaluation Board Test Procedure

![onsemi NCP1230 90 Watt Universal Input Adapter Power Supply Evaluation Board

• fig 39](https://manuals.plus/wp-content/uploads/2024/01/onsemi-NCP1230-90 -Watt-Universal-Input-Adapter-Power-Supply-Evaluation-Board-fig-39.png)Figure

9. NCP1230GEVB Test Setup

Table 2. TEST EQUIPMENT

Test Setup

1. Connect the ac source to the input terminals J4.
2. Connect a variable electronic load to the output terminals J2, the PWB is marked +, for the positive output, and − for the return.
3.  Set the variable electronic load to 45 W.
4. Turn on the ac source and set it to 115 Vac at 60 Hz.
5. Verify that the NCP1230 provides 19 Vdc to the load.
6. Vary the load and input voltage. Verify that the output voltage is within the minimum and maximum values as shown in Table 4.
7. To verify total harmonic distortion (THD) first, shut off the ac power supply.
8. Connect the Voltec Precision Power Analyzer as shown in Figure 9.
9.  Turn on the ac source to 115 Vac at 60 Hz and set the electronic load to 90 W. (Only measure the THD at full load).
10.  Verify that the current Harmonics (THD) are less than the maximum vales in Table 5.
11.  Verify that the PF is greater than the minimum values in Table 5.
12. Set the ac source output to 230 Vac at 60 Hz.
13. Verify that the current Harmonics (THD) are less than the maximum vales in Table 5.
14. Verify that the PF is greater than the minimum values in Table 5.
15. Set the ac source to 115 Vac, set the load to 0 Adc, and measure the standby power, refer to Table 5 for the maximum acceptable input power.
16. Set the ac source to 230 Vac, and refer to Table 5 for the maximum input power.

Table 3. EXPECTED VALUES FOR VARYING INPUT VOLTAGES AND LOADS

Vin (Vac)| Vo (Vdc) @ No Load| Vo (Vdc) @ 45 W| Vo (Vdc) @ 90 W| THD (%)| PF 90 W
---|---|---|---|---|---
90| 19.1| 19.0| 18.8| 6.5| 0.995
115| 19.1| 19.0| 18.8| 7.8| 0.995
230| 18.7| 19.1| 18.8| 20| 0.97

Table 3 shows typical values, the initial set point (19.0 Vdc may vary).
Table 4. REGULATION

Vin (Vac)| Pinmax (W)| Vomin (Vdc)| Vomax (Vdc)| 10 (Adc)| Po (W)| Eff (%)
---|---|---|---|---|---|---
90| 115| 181| 19.1| 4.85| 90| 80.0
115| 114| 18.7| 19.1| 4.85| 90| 80.0
230| 112| 18.7| 19.1| 4.85| 90| 81.0

Table 5. STAND-BY POWER

Table 6. POWER FACTOR AND THD

NCP1230GEVB Figure 10. NCP1230 Demo Board Schematic − PFC section Figure 11. DC−DC section

Table 7. Voltage Regulation and Efficiency

Vin (Vac)| Pin (W)| Vo (Vdc)| Io (Adc)| Po (W)| Eff (%)
---|---|---|---|---|---
85| 54.50| 19.02| 2.36| 45| 82.57
115| 54.40| 19.03| 2.36| 45| 82.72
230| 53.21| 19.06| 2.36| 45| 84.54
265| 53.1| 19.06| 2.36| 45| 84.71
| | | | |
85| 112.00| 18.82| 4.77| 90| 80.36
115| 110.84| 18.88| 4.77| 90| 81.2
230| 109.42| 18.88| 4.77| 90| 82.25
265| 109.01| 18.89| 4.77| 90| 82.56

Table 8. Power Factor and Distortion

Vin (Vac)| Pin (W)| PF| THD (%)| Vo (Vdc)| Po (W)
---|---|---|---|---|---
85| 112.00| 0.996| 6.5| 18.82| 90
115| 110.84| 0.996| 7.7| 18.88| 90
230| 109.42| 0.972| 19.01| 18.88| 90
265| 109.01| 0.965| 23.0| 18.89| 90

Table 9. Standby Power

**Test| Condition (Vac input)| Requirement Pin (mW)| Pin Measured (mW)**
---|---|---|---
Standby Power| 230| 150| 120
Pin Short Circuit| 230| 100| 100
Pin with 0.5 W Load| 230| 800| 600

Table 10. Vendor Contact List

](http://www.cooperet.com/)1−888−414−2645
Panasonic| www.eddieray.com/panasonic.com
Weidmuller| www.weidmuller.com
Keystone| www.keyelco.com 1−800−221−5510
HH Smith| www.hhsmith.com 1−888−847−6484
Aavid Thermalloy| www.aavid.com

Table 11. NCP1230 EVALUATION BOARD BILL OF MATERIALS

**Desig nator| ****QTY| ****Description| Value| ****Toler ance| Footprint| Manufacturer| ****Manufacturer Part Number| Substi- tution Allowed| RoHS**

Com- pliant

---|---|---|---|---|---|---|---|---|---
U9| 1| Flyback Controller| 18 V, 0.5 A| NA| SOIC 8| ON Semiconductor| NCP1230D65R2G| No| Yes
U2| 1| PFC controller| 16 V, 0.6 A| NA| SOIC 8| ON Semiconductor| MC33260DG| No| Yes
U12| 1| Programable reference| 2.5 V| NA| SOIC 8| ON Semiconductor| TL431ACDG| No| Yes
U4| 1| Optocoupler| 70 V, 50 Ma| NA| UL1577| Vishay| SFH615A-3| Yes| Yes
C1, C19| 2| Ceramic chip capacitor| 0.1 uF, 50 V| 10%| 0603| Vishay| VJ0603Y104KXAA| Yes| Yes
C2, C3, C14, C15| 4| Electorlytic Capacitor| 2200 uF, 25 V| 20%| 16.0 mm x 25.0 mm| Vishay| EKB00JG422F00| Yes| Yes
C5| 1| Electorlytic Capacitor| 100 uF, 35 V| 20%| 6.3 mm x
11.0 mm| Vishay| EKB00BA310F00| Yes| Yes
C6| 1| Cap, Ceramic| 0.01uF, 1000V| 10%| Disc| Vishay| 562RZ5UBA102E103M| Yes| Yes
C7, C8| 2| Cap. Aluminum Elec| 47 uF, 25 V| 20%| 5.0 mm x
11.0 mm| Vishay| EKB00AA247F00| Yes| Yes
C10| 1| Capacitor, Y2 class| 2.2 nF, 250 V| 20%| 5.3 mm x
10.3 mm| Vishay| F1710-222-1000| Yes| Yes
C11, C17| 2| Capacitor, X2 class| 0.1 uF, 300 V| 10%| 8.3 mm x
17.8 mm| Vishay| F1772-410-3000| Yes| Yes
C12|

1

| Ceramic chip capacitor| 0.068 uF, 50 V| 10%| 0603| Vishay| VJ0603Y683KXAA| Yes| Yes
C13| 1| Ceramic chip capacitor| 470 pF, 50 V| 10%| 0603| Vishay| VJ0603471KXAA| Yes| Yes
C18| 1| Ceramic chip capacitor| 680 pF, 50V| 10%| 0603| Vishay| VJ0603Y681KXAA| Yes| Yes
C20| 1| Cap. Ceramic, chip| 0.047 uF, 16 V| 10%| 0805| Vishay| VJ0805Y473KXJA| Yes| Yes
C22| 1| Capaitor, X2 class| 0.47 uF, 300 V| 10%| 13.0 mm x 31.3 mm| Vishay| F1772-447-3000| Yes| Yes
C23| 1| Cap. Aluminum| 150uF, 450Vdc| 20%| 25mm x 40mm| Panasonic| ECOS2WP151CA| Yes| Yes
C24| 1| Ceramic chip capacitor| 100 pF, 50 V| 10%| 0805| Vishay| VJ0805100KXAA| Yes| Yes
C25| 1| Ceramic chip capacitor| 1.0 nF, 50 V| 10%| 0805| Vishay| VJ0805Y102KXAA| Yes| Yes
C27| 1| Capacitor, X2 class| 0.22 uF, 300 V| 10%| 10.3 mm x 26.3 mm| Vishay| F1772-422-3000| Yes| Yes
D1| 1| Zener Diode, SM| 13 V, 0.3 W| NA| SOT-23| Vishay| AZ23C13| Yes| Yes
D2, D16| 2| Diode, signal| 75V, 100ma| NA| SOT-23| ON Semiconductor| BAS19LT1G| No| Yes
D4| 1| Diode, ultra fast| 600 V, 1 A| NA| DO41| ON Semiconductor| MUR160| No| Yes
D8, D9, D10, D11| 4| Diode, rectifier| 1000 V, 3 A| NA| DO201AD| ON Semiconductor| 1N5408G| No| Yes
D12| 1| Diode, ultra-fast| 600 V, 4 A| NA| DO201AD| ON Semiconductor| MUR460| No| Yes
D13, D15| 2| Diode, rectifier| 800 V, 1 A| NA| DO41| ON Semiconductor| 1N4006| No| Yes
D17, D18| 2| Zener Diode, SM| 18 V, 0.3 W| NA| SOT-23| Vishay| AZ23C18| Yes| Yes

Table 11. NCP1230 EVALUATION BOARD BILL OF MATERIALS

**Desig nator| QTY| Description| Value| ****Toler ance| Footprint| ****Manufacturer| Manufacturer Part Number| Substitution Allowed| RoHS
Compliant
---|---|---|---|---|---|---|---|---|---
** D19| 1| Diode, schottky| 100 V, 20 A| NA| TO220AB| ON Semiconductor| MBR20100CTG| No| Yes
F1| 1| Brick Fuse| 250 Vac, 2 A| NA| 10mm x 2.5mm| Bussman| 1025TD2| Yes| Yes
J2, J4| 2| PCB Connector| 10 A, 300 V| NA| 5.08 mm| Weidmuller| 171602| Yes| Yes
L1| 1| Inductor| 2.2 uH, 7.5 A| 10%| 13 mm x
9 mm| Coilcraft| DO3316P-222ML| Yes| Yes
L2, L3| 2| Inductor| 100 uH, 2.5 A| 10%| 1315| TDK| TSL1315-101K2R5| Yes| Yes
L4| 1| PFC Indcutor| 400 uH, 5 A| 20%| NA| Cooper Electronics| CTX22-16816| Yes| Yes
L5| 1| Comon Mode Inductor| 508 uH, 3 A| 30%| NA| Coilcraft| E3506-AL| Yes| Yes
Q1| 1| MOSFET 0.8 Ω| 800 V, 11 A| NA| TO220-31| Infineon| SPP11N80C3| Yes| Yes
Q2| 1| MOSFET 0.8 Ω| 650 V, 7.3 A| NA| TO220-31| Infineon| SPP07N60C3| Yes| Yes
Q3| 1| Bipolar transistor| 60 V, 0.6 A| NA| SOT-23| ON Semiconductor| MMBT2907ALT1G| No| Yes
R1, R3| 2| Resistor| 0.4 Ω, 1 W| 1%| 2512| Vishay| WSL2512R4000FEA| Yes| Yes
R2, R18, R29| 3| Resistor| 100k, 3W| 5%| 14.10 mm x 4.57 mm| Vishay| CPF3100k00JNE14| Yes| Yes
R4| 1| Resistor| 49.9 kΩ, 1/8 W| 1%| 0805| Vishay| CRCW08054992FNEA| Yes| Yes
R5, R6, R16| 3| Resistor| 1.3 Ω, 1 W| 1%| 2512| Vishay| CRCW25121R30FNEA| Yes| Yes
R7| 1| Resistor| 4.7 kΩ, 1/8 W| 5%| 0805| Vishay| CRCW8054700RJNEA| Yes| Yes
R10| 1| Resistor| 7.42 kΩ, 1/8 W| 1%| 0805| Vishay| CRCW08057421FNEA| Yes| Yes
R13| 1| Resistor| 20 Ω, 1/4 W| 5%| 1206| Vishay| CRCW120620R0JNEA| Yes| Yes
R17| 1| Resistor| 8.06 kΩ, 1/8 W| 1%| 0805| Vishay| CRCW08058K06FKEA| Yes| Yes
R19, R20| 2| Resistor| 1 MΩ, 1/8 W| 1%| 6.10 mm x 2.29 mm| Vishay| CMF551004FKEK| Yes| Yes
R21, R22| 2| Resistor| 1 kΩ, 1/4 W| 1%| 1206| Vishay| CRCW12061K00FKEA| Yes| Yes
R24| 1| Jumper, 22 AWG| NA| NA| NA| Any| NA| Yes| Yes
R25| 1| Resistor| 200 Ω, 1/4 W| 5%| 1206| Vishay| CRCW1206200RJNEA| Yes| Yes
R26| 1| Resistor| 10 kΩ, 1/4 W| 5%| 1206| Vishay| CRCW120610K0JNEA| Yes| Yes
R27| 1| Resistor| 4.7 Ω, 1/4 W| 5%| 1206| Vishay| CRCW12064R7JNEA| Yes| Yes
R28| 1| Resistor| 200 Ω, 1/4 W| 5%| 1206| Vishay| CRCW1206200RJNEA| Yes| Yes
T1| 1| Flyback Transformer| 220 uH, 3.3
Apk| NA| NA| Cooper Electronics| CTX22-16134| Yes| Yes
H1| 1| Shoulder Washer| NA| NA| #4 x
0.031”| Keystone| 3049| Yes| Yes
H2| 1| Insulator| NA| NA| 0.86 ” x
0.52 ”| Keystone| 4672| Yes| Yes
H3, H4, H5| 3| Heatsink| NA| NA| TO-220| Aavid| 590302B03600| Yes| **** Yes

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The evaluation board/kit (research and development board/kit) (hereinafter the “board”) is not a finished product and is not available for sale to consumers. The board is only intended for research, development, demonstration and evaluation purposes and will only be used in laboratory/development areas by persons with an engineering/technical training and familiar with the risks associated with handling electrical/mechanical components, systems and subsystems. This person assumes full responsibility/liability for proper and safe handling. Any other use, resale or redistribution for any other purpose is strictly prohibited.
THE BOARD IS PROVIDED BY ONSEMI TO YOU “AS IS” AND WITHOUT ANY REPRESENTATIONS OR WARRANTIES WHATSOEVER. WITHOUT LIMITING THE FOREGOING, ONSEMI (AND ITS LICENSORS/SUPPLIERS) HEREBY DISCLAIMS ANY AND ALL REPRESENTATIONS AND WARRANTIES IN RELATION TO THE BOARD, ANY MODIFICATIONS, OR THIS AGREEMENT, WHETHER EXPRESS, IMPLIED, STATUTORY OR OTHERWISE, INCLUDING WITHOUT LIMITATION ANY AND ALL
REPRESENTATIONS AND WARRANTIES OF MERCHANTABILITY, FITNESS FOR A PARTICULAR PURPOSE, TITLE, NON−INFRINGEMENT, AND THOSE ARISING FROM A COURSE OF DEALING, TRADE USAGE, TRADE CUSTOM OR TRADE PRACTICE.
onsemi reserves the right to make changes without further notice to any board.
You are responsible for determining whether the board will be suitable for your intended use or application or will achieve your intended results. Prior to using or distributing any systems that have been evaluated, designed or tested using the board, you agree to test and validate your design to confirm the functionality for your application. Any technical, applications or design information or advice, quality characterization, reliability data or other services provided by onsemi shall not constitute any representation or warranty by onsemi, and no additional obligations or liabilities shall arise from onsemi having provided such information or services.
onsemi products including the boards are not designed, intended, or authorized for use in life support systems, or any FDA Class 3 medical devices or medical devices with a similar or equivalent classification in a foreign jurisdiction, or any devices intended for implantation in the human body. You agree to indemnify, defend and hold harmless onsemi, its directors, officers, employees, representatives, agents, subsidiaries, affiliates, distributors, and assigns, against any and all liabilities, losses, costs, damages, judgments, and expenses, arising out of any claim, demand, investigation, lawsuit, regulatory action or cause of action arising out of or associated with any unauthorized use, even if such claim alleges that onsemi was negligent regarding the design or manufacture of any products and/or the board.
This evaluation board/kit does not fall within the scope of the European Union directives regarding electromagnetic compatibility, restricted substances (RoHS), recycling (WEEE), FCC, CE or UL, and may not meet the technical requirements of these or other related directives.
FCC WARNING – This evaluation board/kit is intended for use for engineering development, demonstration, or evaluation purposes only and is not considered by onsemi to be a finished end product fit for general consumer use. It may generate, use, or radiate radio frequency energy and has not been tested for compliance with the limits of computing devices pursuant to part 15 of FCC rules, which are designed to provide reasonable protection against radio frequency interference. Operation of this equipment may cause interference with radio communications, in which case the user shall be responsible, at its expense, to take whatever measures may be required to correct this interference.
onsemi does not convey any license under its patent rights nor the rights of others.
LIMITATIONS OF LIABILITY: onsemi shall not be liable for any special, consequential, incidental, indirect or punitive damages, including, but not limited to the costs of requalification, delay, loss of profits or goodwill, arising out of or in connection with the board, even if onsemi is advised of the possibility of such damages. In no event shall onsemi’s aggregate liability from any obligation arising out of or in connection with the board, under any theory of liability, exceed the purchase price paid for the board, if any.
The board is provided to you subject to the license and other terms per onsemi’s standard terms and conditions of sale. For more information and documentation, please visit www.onsemi.com.

ADDITIONAL INFORMATION
TECHNICAL PUBLICATIONS:
Technical Library: www.onsemi.com/design/resources/technical−documentation
onsemi Website: www.onsemi.com
ONLINE SUPPORT: www.onsemi.com/support
For additional information, please contact your local Sales Representative at
www.onsemi.com/support/sales
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